Common base

As current is sunk from the emitter, this provides potential difference so causing the transistor to conduct. The current conducted via the collector is proportional to the voltage across the base–emitter junction, accounting for the bias, as with other configurations.[1]

Therefore, if no current is sunk at the emitter, the transistor does not conduct.

This arrangement is not very common in low-frequency discrete circuits, where it is usually employed for amplifiers that require an unusually low input impedance, for example to act as a preamplifier for moving-coil microphones. However, it is popular in integrated circuits and in high-frequency amplifiers, for example for VHF and UHF, because its input capacitance does not suffer from the Miller effect, which degrades the bandwidth of the common-emitter configuration, and because of the relatively high isolation between the input and output. This high isolation means that there is little feedback from the output back to the input, leading to high stability.

This configuration is also useful as a current buffer, since it has a current gain of approximately unity (see formulae below). Often a common base is used in this manner, preceded by a common-emitter stage. The combination of these two form the cascode configuration, which possesses several of the benefits of each configuration, such as high input impedance and isolation.

At low frequencies and under small-signal conditions, the circuit in Figure 1 can be represented by that in Figure 2, where the hybrid-pi model for the BJT has been employed. The input signal is represented by a Thévenin voltage source v_s with a series resistance R_s and the load is a resistor R_L. This circuit can be used to derive the following characteristics of the common base amplifier.

	Definition	Expression	Approximate expression	Conditions
Open-circuit voltage gain	${\displaystyle {A_{v}}=\left.{\frac {v_{\text{o}}}{v_{\text{i}}}}\right|_{R_{L}=\infty }}$	${\displaystyle {\frac {(g_{m}r_{\text{o}}+1)R_{C}}{R_{C}+r_{o}}}}$	${\displaystyle g_{m}R_{C}}$	${\displaystyle r_{o}\gg R_{C}}$
Short-circuit current gain	${\displaystyle A_{i}=\left.{i_{\text{o}} \over i_{\text{i}}}\right|_{R_{L}=0}}$	${\displaystyle {\frac {r_{\pi }+\beta r_{o}}{r_{\pi }+(\beta +1)r_{o}}}}$	${\displaystyle 1}$	${\displaystyle \beta \gg 1}$
Input resistance	${\displaystyle R_{\text{in}}={\frac {v_{i}}{i_{i}}}}$	${\displaystyle {\frac {(r_{o}+R_{C}\|R_{L})r_{E}}{r_{o}+r_{E}+{\frac {R_{C}\|R_{L}}{\beta +1}}}}}$	${\displaystyle r_{e}\left(\approx {\frac {1}{g_{m}}}\right)}$	${\displaystyle r_{o}\gg R_{C}\|R_{L}\ \ \left(\beta \gg 1\right)}$
Output resistance	${\displaystyle R_{\text{out}}=\left.{\frac {v_{o}}{-i_{o}}}\right|_{v_{s}=0}}$	${\displaystyle R_{C}\|\left([1+g_{m}(r_{\pi }\|R_{S})]r_{o}+r_{\pi }\|R_{S}\right)}$	${\displaystyle {\begin{aligned}&R_{C}||r_{o}\\&R_{C}||\left(r_{o}\left[1+g_{m}\left(r_{\pi }||R_{S}\right)\right]\right)\end{aligned}}}$	${\displaystyle {\begin{aligned}R_{S}&\ll r_{E}\\R_{S}&\gg r_{E}\end{aligned}}}$

Note: Parallel lines (||) indicate components in parallel.

In general, the overall voltage/current gain may be substantially less than the open/short-circuit gains listed above (depending on the source and load resistances) due to the loading effect.

Several example applications are described in detail below. A brief overview follows.

• The amplifier input impedance R_in looking into the emitter node is very low, given approximately by

${\displaystyle R_{\text{in}}=r_{E}={\frac {V_{T}}{I_{E}}},}$

where V_T is the thermal voltage, and I_E is the DC emitter current.

For example, for V_T = 26 mV and I_E = 10 mA, rather typical values, R_in = 2.6 Ω. If I_E is reduced to increase R_in, there are other consequences like lower transconductance, higher output resistance and lower β that also must be considered. A practical solution to this low-input-impedance problem is to place a common-emitter stage at the input to form a cascode amplifier.

• Because the input impedance is so low, most signal sources have larger source impedance than the common-base amplifier R_in. The consequence is that the source delivers a current to the input rather than a voltage, even if it is a voltage source. (According to Norton's theorem, this current is approximately i_in = v_S / R_S). If the output signal also is a current, the amplifier is a current buffer and delivers the same current as is input. If the output is taken as a voltage, the amplifier is a transresistance amplifier and delivers a voltage dependent on the load impedance, for example v_out = i_in R_L for a resistor load R_L much smaller in value than the amplifier output resistance R_out. That is, the voltage gain in this case (explained in more detail below) is

${\displaystyle v_{\text{out}}=i_{\text{in}}R_{L}=v_{s}{\frac {R_{L}}{R_{S}}}\Rightarrow A_{v}={\frac {v_{\text{out}}}{v_{S}}}={\frac {R_{L}}{R_{S}}}.}$

Note that for source impedances such that R_S ≫ r_E the output impedance approaches R_out = R_C || [g_m (r_π || R_S) r_O].

• For the special case of very low-impedance sources, the common-base amplifier does work as a voltage amplifier, one of the examples discussed below. In this case (explained in more detail below), when R_S ≪ r_E and R_L ≪ R_out, the voltage gain becomes

${\displaystyle A_{v}={\frac {v_{\text{out}}}{v_{S}}}={\frac {R_{L}}{r_{E}}}\approx g_{m}R_{L},}$

where g_m = I_C / V_T is the transconductance. Notice that for low source impedance, R_out = r_O || R_C.

• The inclusion of r_O in the hybrid-pi model predicts reverse transmission from the amplifiers output to its input, that is the amplifier is bilateral. One consequence of this is that the input/output impedance is affected by the load/source termination impedance, hence, for example, the output resistance R_out may vary over the range r_O || R_C ≤ R_out ≤ (β + 1) r_O || R_C, depending on the source resistance R_S. The amplifier can be approximated as unilateral when neglect of r_O is accurate (valid for low gains and low to moderate load resistances), simplifying the analysis. This approximation often is made in discrete designs, but may be less accurate in RF circuits, and in integrated-circuit designs, where active loads normally are used.

Voltage amplifier

Figure 2: Small-signal model for calculating various parameters; Thévenin voltage source as signal

For the case when the common-base circuit is used as a voltage amplifier, the circuit is shown in Figure 2.

The output resistance is large, at least R_C || r_O, the value which arises with low source impedance (R_S ≪ r_E). A large output resistance is undesirable in a voltage amplifier, as it leads to poor voltage division at the output. Nonetheless, the voltage gain is appreciable even for small loads: according to the table, with R_S = r_E the gain is A_v = g_m R_L / 2. For larger source impedances, the gain is determined by the resistor ratio R_L / R_S, and not by the transistor properties, which can be an advantage where insensitivity to temperature or transistor variations is important.

An alternative to the use of the hybrid-pi model for these calculations is a general technique based upon two-port networks. For example, in an application like this one where voltage is the output, a g-equivalent two-port could be selected for simplicity, as it uses a voltage amplifier in the output port.

For R_S values in the vicinity of r_E the amplifier is transitional between voltage amplifier and current buffer. For R_S >> r_E the driver representation as a Thévenin source should be replaced by representation with a Norton source. The common base circuit stops behaving like a voltage amplifier and behaves like a current follower, as discussed next.

Current follower

Figure 3: Common base circuit with Norton driver; R_C is omitted because an active load is assumed with infinite small-signal output resistance

Figure 3 shows the common base amplifier used as a current follower. The circuit signal is provided by an AC Norton source (current I_S, Norton resistance R_S) at the input, and the circuit has a resistor load R_L at the output.

As mentioned earlier, this amplifier is bilateral as a consequence of the output resistance r_O, which connects the output to the input. In this case the output resistance is large even in the worst case (it is at least r_O || R_C and can become (β + 1) r_O || R_C for large R_S). Large output resistance is a desirable attribute of a current source because favorable current division sends most of the current to the load. The current gain is very nearly unity as long as R_S ≫ r_E.

An alternative analysis technique is based upon two-port networks. For example, in an application like this one where current is the output, an h-equivalent two-port is selected because it uses a current amplifier in the output port.

• Common collector
• Common emitter
• Common gate
• Common drain
• Common source
• Differential amplifier
• Hybrid-pi model
• Two-port network

• Basic BJT Amplifier Configurations (archived from the original on September 9, 2007)
• NPN Common Base Amplifier — HyperPhysics
• ECE 327: Transistor Basics — Gives example common base circuit (i.e., current source) with explanation.